slyy154a___Simplifying Current Sensing

Chapter 5: Wide VIN and isolated current measurement

Assuming the application of a full-scale sine wave of Depending on the input-voltage range of the ADC, you
±250mV at VIN, the internal gain of the AMC1301 will can incorporate gain or attenuation into the differential
provide 2.05 V peak-to-peak outputs at points VOUTP to single-ended stage to adjust the output swing. The
and VOUTN, which are 180 degrees out of phase. The output common-mode voltage is adjustable to fit the
difference between these signals, VODIF, is 4.1 V peak to input needs of the ADC as well.
peak. When R1 = R4 and R2 = R3, Equation 1 shows
the transfer function of the output stage: Design example

VOUT = VOUTP ´ æ R4 ö + VOUTN ´ æ R1 ö + VCM The embedded ADC found on most MSP430 devices
ç R3 ÷ ç R2 ÷ has an input-voltage range of 0 V-2.5 V when using the
è ø è ø internal voltage reference. Using the VOUTP from the
AMC1301 would give the ADC an input signal ranging
With equal-value resistors for R1 through R4 in from 0.415 V to 2.465 V, well within the input range of
Equation 1 and VCM set to 2.5 V, Equation 1 reduces to the converter while using only half the input range of the
Equation 2: AMC1301. As shown in Figure 5, by using a differential
to single-ended amplifier configuration with a gain of
VOUT = (VOUTP - VOUTN)+ VCM 0.5 and a common-mode voltage of 1.25 V, the entire
voltage range of the AMC1301 is applicable to the ADC.

The plots in Figure 4 show the input and output voltages R1 4.99 K
of the AMC1301, along with the output voltage of
the final differential to single-ended output stage. The VDD1
differential voltage of ±2.05 V transposes to a single-
ended signal from 0.5 V to 4.5 V. U1 1 VDD2 VDD2
AMC1301
8 VOUTN 5
2 + V+ V+
7 R2 10.0 K 3 – V+ 4
VIN V– 6 1
+ V– VOUT
3
– V– R3 10.0 K U2
5 VOUTP 2 TLV6001
2.50.00m

1.) VIN 0.00 4 R4 4.99 K

GND1 GND2 GND2

–2.50.00m GND1 VCM
3.00 1.25 V

2.) VOUTP 1.50 Figure 5: Scaled differential to single-ended output

0.00 While it is possible to use a single output of the
3.00 AMC1301 to drive a single-ended ADC, adding a
differential to single-ended operational-amplifier stage at
3.) VOUTN 1.50 the output ensures that the target application will have
the largest possible dynamic range.
4.) VODIF 0.00
2.50
0.00

–2.50 Alternative device recommendations
5.00
The AMC1100 or AMC1200 provide basic isolation with
5.) VOUT 2.50 similar performance to the AMC1301 at a lower price
point. For applications requiring a bipolar output option,
0.00 50.00 µ 100.00 µ 150.00 µ 200.00 µ the TLV170 is an excellent choice.
0.00 Time (s)

Figure 4: Single-ended output voltage

Current Sense Amplifiers 51 Texas Instruments

Chapter 5: Wide VIN and isolated current measurement

Device Optimized parameters Performance trade-off
Lower transient immunity
AMC1100 Galvanic isolation up to 4,250 VPEAK Basic isolation vs. reinforced
Higher input bias current
AMC1200 Galvanic isolation up to 4,250 VPEAK

TLV170 Bipolar operation to ±18 V

Table 1: Alternative device recommendations

SBOA161B “Low-Drift, Low-Side Current Measurements for Three-Phase Systems”

SBOA165B “Precision Current Measurements on High Voltage Power Supply Rails”

Table 2: Related TI application notes

Extending beyond the maximum common-mode input common mode needs to be divided down to a
range of discrete current-sense amplifiers 40 V common-mode voltage. You can divide this voltage
using external resistor dividers, as shown in Figure 1.
For high-side power-supply current-sensing needs, you
must know the maximum voltage rating of the power This is a simple design approach, however, and the
supply. The maximum power-supply voltage will drive trade-offs are significant. The gain error and common-
current-sense amplifier selection. The common-mode mode rejection ratio (CMRR) of the amplifier depend
voltage of the current-sense amplifier should exceed the on the accuracy and the matching of the external input
maximum voltage on the power supply. For example, divider resistors. Apart from gain error and CMRR errors,
if you are measuring current on the 48V power supply the tolerance of the external resistors will contribute to
with a transient voltage not exceeding 96V, you’ll need an imbalance in the input voltage, causing additional
to design a current-sense amplifier with a maximum output errors. This error does increase over temperature,
common-mode voltage supporting 96 V. For a 400 V depending on the drift specifications of the resistors.
supply, you’ll need to choose a current-sense amplifier One technique to minimize output error is to use
with a common-mode voltage supporting 400V. precision 0.1%-matched low-temperature-drift
external resistor dividers.
The cost of high-voltage, high-side current sensing
can be expensive if you need to achieve a goal of <1% Power R1 R2
accuracy. For common-mode voltages higher than supply IN+
90 V, the selection of a current-sense amplifier is often IN– R3 VOUT = G x (V(IN+) – V(IN-))
limited to isolation technology, which can be expensive RSHUNT G = R2/R1
and bill-of-materials (BOM)-extensive. But it is possible
to extend low-voltage common-mode current-sense Load R4
amplifiers beyond their maximum ratings by adding a few
inexpensive external components like resistors, diodes Power
and p-channel metal-oxide semiconductor (PMOS) field- supply
effect transistors (FETs).
V+ RD1 R1 R2
Common-mode voltage divider using resistors RSHUNT R4
IN+ VOUT = G x (VCMP-VCMN)
The simplest approach to monitoring high-voltage V– G = (R2/R1)
high-side current sensing is a design with a low-voltage RD3 RD2
current-sense amplifier with external input-voltage Load R3 VCMP = V(+) x (RD2/(RD2+RD1)
dividers. For example, if you select a 40 V common- VCMN = V(–) x (RD4/(RD4+RD3)
IN–
RD4

mode voltage amplifier for an 80 V application, the 80 V Figure 1: Extending the common-mode range using resistor dividers

Current Sense Amplifiers 52 Texas Instruments

Chapter 5: Wide VIN and isolated current measurement

Extending the common-mode range for current 400 V
output amplifiers
5K INA168
Because voltage dividers have serious consequences IN+ R2 200 µA/V
with output error and performance degradation, another
approach is to shift the ground reference of the current- RSHUNT +
output amplifier to the high-voltage common-mode DZ1
node, as shown in Figure 2. Figure 2 enables current
sensing at higher voltages beyond the rated common- 5K –
mode voltage of the INA168, which is 60V. You can
extend this technique to any voltage beyond 60V by IN–
designing an appropriate PMOS FET (Q1).
Load Q1
In Figure 2, Zener diode DZ1 regulates the supply R1
voltage in which the current shunt monitor operates, VOUT
and this voltage floats relative to the supply voltage.
DZ1 provides a sufficient operating voltage for the RL
combination of IC1 and Q1 over the expected power- 50 K
supply range (typically from 5.1 V to 56 V). Select R1 to
set the bias current for DZ1 at some value greater than Figure 2: High-side DC current measurements for 400V systems
the maximum quiescent current of IC1.
Extending the common-mode voltage range for
The INA168 shown in Figure 2 is specified at 90 power monitors
μA maximum at 400 V. The bias current in DZ1 is
approximately 1mA at 400 V, well in excess of IC1’s System optimization and power monitoring for high-
maximum current (the bias current value selected voltage systems (40 V to 400 V), if implemented
limits dissipation in R1 to less than 0.1W). Connecting accurately, can result in improved system power
a p-channel metal-oxide semiconductor field-effect management and efficiency. Knowing current, voltage
transistor (MOSFET), Q1, cascodes the output current and system power information can be beneficial in
of IC1 down to or below ground level. Transistor Q1’s diagnosing faults or calculating the system’s total power
voltage rating should exceed the difference between the consumption. Monitoring faults and power optimization
total supply and DZ1 by several volts because of the can prevent premature failures and significantly lower
upward-voltage swing on Q1’s source. Select RL, IC1’s power savings by optimizing system shutdown and
load resistor, as if IC1 were used alone. The cascode wake up.
connection of Q1 enables the use of IC1 well in excess
of its normal 60V rating. The example circuit shown in Figure 3 illustrates a methodology by using the INA226,
Figure 2 was specifically designed to operate at 400 V. a 36 V common-mode voltage power-monitoring device,
for applications supporting 40 V-to-400 V systems.
Figure 2 shows is the precision, rail-to-rail OPA333
operational amplifier (op amp) used to mirror the
sense voltage across the shunt resistor onto precision
resistor R1. The OPA333 is floated up to 400 V using
a 5.1 V Zener diode between its supply pins. The op
amp drives the gate of the 600 V PFET in a current
follower configuration. Choosing a low-leakage PFET
enables accurate readings even at the low end of the
measurement.

Current Sense Amplifiers 53 Texas Instruments

Chapter 5: Wide VIN and isolated current measurement

The voltage across R1 sets the drain current of the FET. 400 V VSENSE 5.1 V
By matching the resistor R2 in the drain of the FET to – Zener
be equal to R1, the VSENSE voltage develops across + 10 K OPA333
R2 (VR2). Inputs of the INA226 current monitor connect RSHUNT + +
across R2 for current sensing. Thus, the current monitor
does not need the high-common-mode capability, as it Load 10 K
will only see common-mode voltages around VSENSE, SENSEV
which are usually less than 100 mV. SENSEV IN+ VBUS SCL
221100RR IN– GND SDA
The INA226 is a high-accuracy current/voltage/power
monitor with an I2C interface. The INA226 can also RZ
sense bus voltages less than 36V. Since the bus voltage
employed here is 400 V, a divider scales down the high- Figure 3: High-voltage power monitoring
voltage bus to a voltage within the common-mode range
of the INA226. With a ratio of 64, the bus voltage’s least
significant bit (LSB) can scale accordingly to obtain the
actual bus voltage reading. In this case, you could use a
modified LSB of 80 mV. Choosing precision resistors for
the divider helps maintain the accuracy of the
bus measurement.

Device Optimized parameters Performance trade-off
Slew rate: 0.5 V/µS
LMP8645HV Bandwidth: 900 kHz, package: small-outline Gain error (1%), shunt offset
transistor (SOT)-23-6 voltage: 100 µV
Offset voltage: 1 mV
INA220 Mini small-outline package (MSOP)-8, I2C interface,
selectable I2C address

INA139 Package: SOT-23, bandwidth: 4,400kHz, cost

Table 1: Alternative device recommendations

SBOA174A “Current Sensing in an H-Bridge”

SBOA176A “Switching Power Supply Current Measurements”

SBOA166B “High-Side Drive, High-Side Solenoid Monitor with PWM Rejection”

Table 2: Related TI application notes

Current Sense Amplifiers 54 Texas Instruments

Chapter 5: Wide VIN and isolated current measurement

Low-Drift, Precision, In-Line Isolated Magnetic phase to large voltage transients that switch between the
Motor Current Measurements positive and negative power rails every cycle. An ideal
current sensor has the ability to completely reject the
The demand for higher efficiency systems continues to common-mode voltage component of the measurement,
increase, leading to direct pressure for improvement in and only measure the current of interest. In-package
motor operating efficiency and control. This focus applies magnetic current sensors like the TMCS1100 pass the
to nearly all classes of electric motors, including those phase current through a package leadframe, which
used in: creates an internal magnetic field. A galvanically isolated
sensor then measures the magnetic field, providing a
• White goods measurement of the current without any direct electrical
connection between the sensor IC and the isolated
• Industrial drives phase current. By measuring only the magnetic field,
the sensor provides isolation to high common-mode
• Automation voltages, as well as excellent immunity to PWM switching
transients. This results in excellent motor phase current
• Automotive applications measurements without unwanted disturbances at the
sensor output due to large, PWM-driven input voltage
This is especially true in higher-power systems with steps. Figure 2 illustrates an RC-filtered TMCS1100
elevated operating voltages. Operational characteristics output waveform, along with the motor phase voltage
of the motor fed back into the control algorithm are and current waveforms. Only minor PWM-coupling
critical to ensure the motor is operating at peak efficiency due to measurement parasitics are observable, and
and performance. Phase current is one of these critical the TMCS1100 output tracks the motor phase current
diagnostic feedback elements used by the system with no significant output transients due to the 300-V
controller to enable optimal motor performance. switching events.

Due to the continuity of the measurement signal and
direct correlation to the phase currents, an ideal location
to measure the motor current is directly in-line with each
phase, as shown in Figure 1. Measuring current in other
locations, such as the low-side of each phase, requires
recombination and processing before meaningful data
can be used by the control algorithm.

To Controller Figure 2. Motor Phase Current Measurement with High
Figure 1. In-Line Current Sensing Transient Immunity

The drive circuitry for the motor generates pulse width The unique characteristics of an in-package magnetic
modulated (PWM) signals to control the operation current sensor eliminate many of the challenges faced by
of the motor. These modulated signals subject the alternative solutions to measuring motor phase currents.
measurement circuitry placed in-line with each motor The inherent galvanic isolation provides capability to
withstand high voltage, and the high transient immunity

Current Sense Amplifiers 55 Texas Instruments

Chapter 5: Wide VIN and isolated current measurement

of the output reduces output noise due to switching 1
events. Current sensing implementations without this
immunity require higher bandwidth in order to improve Sensitivity Error (%) 0.5
output glitch settling time; a magnetic sensor can use a
lower-bandwidth signal chain without sacrificing transient 0
immunity performance. In-package magnetic current
sensors also provide a reduction in total solution cost -0.5
and design complexity due to no requirement for external
resistive shunts, passive filtering, or isolated power -1
supplies relative to the high voltage input. -40 -20 0 20 40 60 80 100 120
Temperature (°C)
For applications where phase current measurements D006
provide over-current protection or diagnostics, the
high transient rejection of a magnetic current sensor Figure 3. TMCS1100 Typical Sensitivity Error Across Temperature
prevents false overcurrent indications due to output
glitches. In motor systems where closed loop motor In addition to high-sensitivity accuracy, the device has less
control algorithms are used, precise phase current than 2 mV of output offset drift, shown in Figure 4, which
measurements are needed in order to optimize motor greatly improves measurement dynamic range, and allows
performance. Historically, Hall-based current sensors for precise feedback control even at light loads.
have suffered from large temperature, lifetime, and
hysteresis errors that degrade motor efficiency, dynamic 5 TMCS1100A1
response, and cause non-ideal errors such as torque TMCS1100A2
ripple. Common system-level calibration techniques can 4.5
improve accuracy at room temperature, but accounting
for temperature drift in parameters, such as sensitivity 4 TMCS1100A3
and offset, is challenging. TMCS1100A4
Typical Offset (mV) 3.5
Magnetic current sensing products from Texas
Instruments improve system-level performance by 3
incorporating patented linearization techniques and
zero-drift architectures that provide stable, precise 2.5
current measurements across temperature. A high-
precision sensor tightly controls phase-to-phase current 2
measurement errors, maintaining accurate feedback
control and delivering a seamless user experience. 1.5

The TMCS1100 features less than 0.3% typical 1
sensitivity error at room temperature, and less than
0.85% maximum sensitivity error across the entire 0.5
temperature range from –40°C to 125°C. This stability
across temperature, shown in Figure 3, provides 0
excellent phase-to-phase matching by minimizing the -40 -20 0 20 40 60 80 100 120
temperature drift of the sensor. Temperature (°C)
D009

Figure 4. TMCS1100 Typical Output Offset Across Temperature

Combining high-sensitivity stability and a low offset
results in an industry-leading isolated current sensing
solution with <1% total error across the full temperature
range of the device. A 600-V working voltage and 3
kV isolation barrier allows the device to fit into a wide
array of high voltage systems. Combining measurement
temperature stability, galvanic isolation, and transient

PWM input rejection, the TMCS1100 is an ideal choice
for PWM-driven applications, such as motor phase
current measurements, where accurate and reliable
measurements are required for precisely controlled

performance.

Current Sense Amplifiers 56 Texas Instruments

Chapter 5: Wide VIN and isolated current measurement

Device Optimized Parameter Performance Trade-Off
Lower precision, PSRR
TMCS1101 Magnetic Current Sensor with Internal Reference Solution size, complexity
80V functional isolation
AMC1300 Reinforced Isolation Shunt Amplifier
80V Functional isolation, size
INA240 Precision Shunt Amplifier with PWM Rejection

INA253 Precision Integrated-Shunt Amplifier with PWM
Rejection

Table 1. Alternate Device Recommendations

Lit # Title

SBOA340 Ratiometric Versus Non-Ratiometric Magnetic Signal Chains

SBOA160 Low-Drift, Precision, In-Line Motor Current Measurements With PWM Rejection

SBOA161 Low-Drift, Low-Side Current Measurements for Three- Phase Systems

SBOA163 High-Side Motor Current Monitoring for Over-Current Protection

Table 2. Related TI TechNotes

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Integrating the Current Sensing Signal Path

Scott Hill, Current Sensing Products

Current measurements are used in electronic systems To optimize the current sensing signal chain, the shunt
to provide feedback verifying operation is within resistor value and amplifier gain must be appropriately
acceptable margins and to detect potential fault selected for the current range and full-scale input
conditions. Analyzing a system’s current level can range of the ADC. The selection of the shunt resistor
diagnose unintended or unexpected operating modes is based on a compromise between measurement
allowing for adjustments to be made to improve accuracy and power dissipation across the shunt
reliability or to protect the system components from resistor. A large value resistor will develop a larger
damage. differential voltage as the current passes through. The
measurement errors will be smaller due to the fixed
Current is a signal that is difficult to measure directly. amplifier offset voltage. However, the larger signal
However, there are several measurement methods creates a larger power dissipation across the shunt
that are capable of measuring the effect of flowing resistor (P = I2R). A smaller shunt resistor develops a
current. Current passing through a wire produces a smaller drop across the shunt resistor reducing the
magnetic field that can be detected by magnetic power dissipation requirements but also increases the
sensors (hall-effect and fluxgate for example). Current measurement errors as the amplifier’s fixed offset
measurements can also be made by measuring the errors become a larger percentage of the signal.
voltage developed across a resistor as current passes
through. This type of resistor is called a current The amplifier gain is selected to ensure that the
sensing, or shunt, resistor. amplifier’s output signal will not exceed the ADCs full-
scale input range at the full-scale input current level.
For current ranges reaching up to 100 amps on
voltage rails below 100 volts, measuring current with The INA210 is a dedicated current sense amplifier that
shunt resistors are typically preferred. The shunt integrates the external gain setting resistors as shown
resistor approach commonly provides a physically in Figure 2. Bringing these gain resistors internal to the
smaller, more accurate and temperature stable device allows for increased matching and temperature
measurement compared to a magnetic solution. drift stability compared to typical external gain setting
resistors. Space saving QFN packages significantly
For the system’s current information to be evaluated reduce the board space requirements of an
and analyzed, it must be digitized and sent to the operational amplifier and external gain resistors.
system controller. There are many methods for Current sense amplifiers are commonly available in
measuring and converting the signal developed across multiple fixed gain levels to better optimize the pairing
the shunt resistor. The most common approach with shunt resistor values based on the input current
involves using an analog front-end to convert the and ADC full-scale input ranges.
current sensing resistor’s differential signal to a single-
ended signal. This single-ended signal is then VCM = VS =
connected to an analog to digital converter (ADC) that
is connected to a microcontroller. Figure 1 illustrates 0V to 26V 2.7V to 26V
the current sensing signal chain.

SUPPLY INA210

POWER
SUPPLY

RSHUNT + ADC CONTROLLER RSHUNT +
- REF
LOAD REF VOUT

-

LOAD

Figure 1. Current Sensing Signal Path Figure 2. INA210: Current Sensing Amplifier

SBOA167A – July 2016 – Revised December 2016 Integrating the Current Sensing Signal Path Scott Hill, Current Sensing Products 1

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Figure 1 shows the operational amplifier measuring www.ti.com
the differential voltage developed across the shunt
resistor and sending the amplified signal to the single In addition to the ability to directly measure voltage
ended ADC. A fully differential input ADC can monitor developed across the shunt resistor as current passes
the differential voltage directly across the shunt through, the INA226 can also measure the common-
resistor. One drawback to using a typical ADC is mode voltage. The INA226 has an input multiplexer
reduced input range used. The signal developed allowing the ADC input circuitry to switch between the
across a shunt resistor will be small to limit the power differential shunt voltage measurement and the single-
dissipation requirements of this component. Lower ended bus voltage measurement.
ADC resolutions will also impact the small signal
measurement accuracy. The current sensing resistor value present in the
system can be programmed into a configuration
The ADC reference will also be an additional error register on the INA226. Based on this current sensing
source that must be evaluated in this signal path. A resistor value and the measured shunt voltage, on-
typical ADC will feature an input range that is based chip calculations convert of the shunt voltage back to
on the converter's reference voltage. The actual current and can provide a direct readout of the
reference voltage range varies from device to device corresponding power level of the system. Performing
but is typically in the 2V to 5V range. The LSB (least these calculations on-chip reduces processor
significant bit) is based on the full-scale range and resources that would normally be required to convert
resolution of the converter. For example, a 16-bit this information.
converter with a full-scale input range of 2.5V, the LSB
value is roughly 38µV. Alternate Device Recommendations

The INA226 is a specialized ADC designed specifically For applications with lower performance requirements,
for bi-directional current sensing applications. Unlike using the INA199 still takes advantage of the benefits
typical ADCs, this 16-bit converter features a full-scale of the dedicated current sense amplifier. For
input range of +/- 80mV eliminating the need to amplify applications implementing over-current detection, the
the input signal to maximize the ADC's full-scale input INA301 features an integrated comparator to allow for
range. The INA226 is able to accurately measure on-chip over-current detection as fast as 1µs. For
small shunt voltages based on the device's maximum applications with lower performance requirements,
input offset voltage of 10µV and an LSB size of 2.5µV. using the INA219 is able to take advantage of the
The INA226 provides 15 times more resolution than specialized current sensing ADC.
the equivalent standard 16-bit ADC with a full-scale
input range of 2.5V. The specialization of the INA226 Table 1. Alternative Device Recommendations
makes this device ideal for directly monitoring the
voltage drop across the current sensing resistor as Device Optimized Parameter Performance Trade-
shown in Figure 3. INA199 Off
INA301 Lower Cost
Supply Signal Bandwidth, On- Higher VOS & Gain Error
INA219 Larger Package:
2.7V to 5.5V Board Comparator MSOP-8
Smaller Package Digital
VCM = Higher VOS & Gain Error
0V to 36V Monitor, Lower Cost

Table 2. Related TI TechNotes

Alert GPIO SBOA162 Measuring Current To Detect Out-of-Range
RSHUNT SBOA165 Conditions
CONTROlLERSDASBOA160
16-Bit I2C SCL SBOA161 Precision Current Measurement On High
ADC Interface Voltage Power Rail

INA226 High Precision, Low-Drift In-Line Motor
Current Measurements
LOAD
Low-Drift, Low-Side Current Measurements
for Three-Phase Systems

Figure 3. Digital Current/Power Monitor

2 Integrating the Current Sensing Signal Path Scott Hill, Current Sensing Products SBOA167A – July 2016 – Revised December 2016

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Precision, low-side current measurement

Dennis Hudgins, Current Sensing Products

For most applications, current measurements are circuits are referenced to the supply ground. To
made by sensing the voltage drop across a resistor. minimize this issue, reference all circuits that have
There are two locations in a circuit that resistors are interactions to the same ground. Reducing the value of
commonly placed for current measurements. The first the current sense resistor helps minimize any ground
location is between the power supply and load. This shifts.
measurement method is referred to as high-side
sensing. The second location a sense resistor is Low-side current sensing is the easiest method to use
commonly placed is between the load and ground. when designing circuits or choosing devices to do
This method for sensing the current is referred to as current measurements. Due to the low common mode
low-side current sensing. Figure 1 shows the two voltage at the inputs, a difference amplifier typology
methods to sense current in a load. can be used. Figure 2 shows the classical difference
amplifier typology using an operational amplifier (op-
Power amp).
Supply
Power
Supply

Current Flow +
Direction
High-Side VOUT R2 V1 V2
RSENSE Sensing R1

- Common-mode voltage LOAD
(VCM) is supply dependent
V1
+ R1 R2

LOAD RSENSE
-
Current Flow + +
Direction V2
VOUT
RSENSE
Low-Side Common-mode voltage - R2
Sensing is always near ground and is
isolated from supply spikes R1
-

Figure 1. Current Sensing Methods Figure 2. Operational Amplifier Configuration for
Low-Side Sensing
There are advantages and disadvantages of doing
either measurement. One of the advantages of low- When using an op-amp for current sense
side current measurements is the common-mode measurements, there are several performance
voltage, or the average voltage at the measurement requirements that need to be met to ensure correct
inputs is near zero. This makes it easier to design operation. First, the operation amplifier needs to
application circuits or select devices for this support common-mode input voltages to ground when
measurement. Since the voltages seen by the current operated from a signal supply. Since the difference
sensing circuit are near the ground, this is the amplifier typically gains the differential input signal, the
preferred method of measuring currents when dealing swing to rail specification of the op-amp is important in
with very high voltages, or in applications where the order to ensure the signal is correctly passed to the
supply voltage may be prone to spikes or surges. The output. For these reasons, rail-to-rail input and output
immunity to high voltage spikes and ability to monitor operation amplifiers are generally preferred for current
currents in high-voltage systems make low-side sense measurements. Since operational amplifiers are
current sensing popular in many automotive, industrial, not specified in the difference amplifier configuration, it
and telecommunication applications. The major is difficult to tell what the performance can be in the
disadvantage of low-side current sensing is that the real application. Parameters such as slew rate,
voltage drop across the sense resistor appears as a bandwidth, input current, common mode rejection, and
difference between the supply ground and the drift are all degraded when resistors around the op-
load/system ground. This can be an issue if other amp are added to create the current sense circuit. The
parametric degradation depends on the closed loop

SBOA169B – October 2016 – Revised March 2019 Precision, low-side current measurement Dennis Hudgins, Current Sensing Products 1

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resistors. Figure 2 shows the matching and tolerance
of R1 and R2. They need to be considered when area, and simplifies the layout. Integration of these
implementing a discrete solution since variations in resistors does not necessarily mean an increase in
these components directly affect the circuit gain error. package size. The INA199 is available both in the 2-
mm x 1.25-mm SC70-6 leaded package and the 1.8-
Another factor to consider when implementing a mm x 1.4-mm UQFN package.
discrete current sense amplifier is the PCB layout. R1
and R2 need placed as closely as possible to the The current measurement accuracy of the INA199 is
operational amplifier and current sense resistor. By better than what is achievable with cost effective
placing these components close the op-amp the discrete op-amp designs. The device features a
likelihood of noise pickup on the operational amplifier maximum gain error of 1.5% over the temperature
positive input is reduced. Since many current sense range of -40°C to 105°C. The offset of the INA199 is
amplifiers are used with DC/DC convertors, the less than 150 μV and drifts less than 0.5 μV/°C.
placement of the entire current sense circuit needs to
be carefully considered to avoid radiated noise by the The INA199 also features a REF pin. The voltage
DC/DC power supplies. Figure 2 shows how to applied at the REF pin adds to the voltage seen at the
calculate the difference amplifier gain. However, any output. This is useful if down-stream devices need to
increase or decrease in the gain affects the solution have the current signal level-shifted.
stability and bandwidth. The stability of the op-amp
requires special consideration in applications where a Alternate Device Recommendations
capacitive load is present to avoid oscillations or
excessive output ringing. For a smaller current sense solution with improved
accuracy, the INA185 provides 0.2% gain error in the
Figure 3 shows a current sense amplifier, which is an very small SOT-563 package. For applications
effective way to address the weaknesses of the requiring higher performance, the INA210-215 series
discrete implementation. of devices provide low offset (35 μV maximum) and
gain error (1% Max). If a high accuracy current monitor
Power with a digital interface is needed, the INA226 features
Supply a maximum offset of 10 μV and a gain error of 0.1%. If
a small digital based current monitor is needed, the
LOAD Reference INA231 is offered in a tiny 1.68-mm x 1.43-mm
Voltage package and is well-suited for portable or other space
VS = 2.7 V to 26 V constrained applications. If a voltage output current
REF monitor is needed with pin strappable gain settings,
use the INA225.
OUT
IN+ Table 1. Alternative Device Recommendations

RSENSE + DEVICE OPTIMIZED PARAMETERS PERFORMAN
- CE TRADE-
IN- INA185 Solution size, Accuracy
GND INA210 Accuracy OFF
INA215
Figure 3. Low-Side Current Sensing with INA199 INA231 Digital interface, small size Slightly higher
Current Sense Amplifier INA226 Digital interface, high accuracy cost

A current sense amplifier integrates the gain setting Slightly higher
resistors, reducing many of the layout concerns that cost
exist with discrete implementations. The internal
resistors are designed to reduce mismatch, which Cost
optimizes the gain error specification. Current sense
amplifiers come preconfigured to address many Package size,
different gain requirements. For example, the INA199 cost
is available with gains of 50, 100, and 200 V/V. The
bandwidth and capacitor load stability is optimized for Table 2. Related Documentation
each gain setting with maximum capacitive loads
specified in the datasheet. Integration of the gain SBOA161 Low-Drift, Low-Side Current Measurements
setting resistors reduces noise susceptibility, PCB SBOA167 for Three Phase Systems
SBOA165
Integrating The Current Sensing Signal Path

Precision Current Measurements on High-
Voltage Power Supply Rails

2 Precision, low-side current measurement Dennis Hudgins, Current Sensing Products SBOA169B – October 2016 – Revised March 2019

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____________________________________________________

Integrating the Current Sensing Resistor

Scott Hill, Current Sensing Products

1 Current is one of the most common signals Amplifiers have fixed inherent errors associated with
used for evaluating and diagnosing the them, input offset voltage for example, that impact the
operational effectiveness of an electronic measurement accuracy. As the input signal increases,
system. However, measuring this signal directly the influence of these internal errors on the total
is very challenging. Instead, many types of measurement accuracy decreases. When the input
sensors are used to measure the proportional signal decreases the corresponding measurement
effects that occur due to current flowing error is a higher . This relationship between the signal
throughout the system. level and the acceptable measurement accuracy
provides general lower limits for the current sensing
The most common sensing element used for detecting resistor selection. The upper limit value for the current
current flowing in a system is a resistor. Placing a sensing resistor should be limited based on an
resistor, called a shunt, in series with the current path application’s acceptable power loss for this
develops a differential voltage across the resistor as component.
current passes through it.
One benefit of using resistors for current measurement
One common signal chain configuration for monitoring is the availability of accurate components that provide
a current signal involves an analog front-end (AFE), an both high precision and temperature stable
analog to digital converter (ADC), and a system measurements. Precision current sensing amplifiers
controller as shown in Figure 1. An AFE, such as an are available featuring measurement capabilities
operational amplifier or dedicated current sense optimized for interfacing with very small signals to
amplifier, converts the small differetial voltage accommodate small value resistors and low power
developed across the shunt resistor to a larger output losses.
voltage that the ADC can digitize before sending the
information to a controller. The system controller uses There are two trends for resistors as the ohmic value
the current information to optimize the system's decreases into the single digit milliohm level and
operational performance or reduce functionality in the below. One trend for this segment of resistors is the
event of an out-of-range condition to prevent potential reduced package availability and resistor value
damaging conditions from occurring. combinations. The other trend is the increased cost for
precision and low temperature coefficient components.
+ Pairing a low ohmic, low temperature coefficient
current sensing resistors with precision tolerance
ADC CONTROLLER levels (~0.1%) result in solution costs in the several
dollar range without including the cost associated with
Figure 1. Current Sensing Signal Chain the precision amplifier.

The proper resistance value selection is critical in A component such as the INA250, shown in Figure 2,
optimizing the signal chain path. The resistance value helps reduce the challenges of selecting these
and corresponding voltage developed across the shunt increased accuracy, higher cost resistors for
results in a system power loss. To limit the power applications needing precise and temperature stable
loss, it is preferred to minimize the shunt resistance. measurements. This device pairs a precision, zero-
The resistor value is directly proportional to the signal drift, voltage output current sense amplifier with a 2mΩ
developed and sent to the current sensing amplifier. integrated current sensing resistor with a 0.1%
maximum tolerance and a temperature drift of
15ppm/ºC over the device's entire tempeature range of
-40ºC to +125ºC. This device can accommodate
continuous currents flowing through the on-board
resistor of up to 15A.

SBOA170B – October 2016 – Revised July 2018 Integrating the Current Sensing Resistor Scott Hill, Current Sensing Products 1

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Supply 0V to 36V Supply
Voltage

0V to 36V VS INA250 Load IN+ VBUS INA260 SDA SDA
Supply SCL SCL
IN+ IN- V

I2C GPIO
Interface Alert
ADC

- A0
+
A1 Controller
ADC I
Reference
Voltage Controller IN- GND

REF OUT

ADC Load

GND Figure 3. Integrated Signal Path

Figure 2. Integrating The Current Sensing Resistor Pairing the precision, low-drift current sensing with
these precision current sensing devices provides
In addition to the integrated precision resistor inside measurement solutions that are challenging to
this device, the INA250 also addresses one of the accomplish using discrete amplifier and resistor
most common issues associated with implementing a combinations. There are few catalog current sensing
current sensing solution. A low-ohmic shunt resistor is resistors available that are capable of enabling the
used to reduce the current sensing power dissipation. combination of precision and temperature stable
A challenge in accommodating this low resistance measurements but achieving this level of accuracy in a
value is the potential impact of parasitic resistance on solution size comparable to TSSOP-16 packaged
the PCB. Parasitic resistance in series with the shunt integrated solutions doesn't exist.
resistor can cause additional measurement errors as
current flows through the resistance to create the Alternate Device Recommendations
shunt voltage. The most common source for these
measurement errors is poor layout techniques. A For additional design flexibility, many stand-alone
Kelvin connection, also known as a four terminal current sensing amplifiers and digital power monitors
connection or a force-sense, is required to ensure that are also available. For lower performance applications
minimal additional resistance is present to alter the with higher current requirements than the integrated
differential voltage developed between the amplifier's solutions support, use the INA210 stand-alone current
input pins. There are PCB layout techniques to reduce sensing amplifier. For applications requring a stand-
the effect of parasitic resistance, however, this alone digital power monitor, use the INA226. For
concern is removed with the INA250. applications implementing over-current detection, the
INA301 features an integrated comparator for on-chip
For applications that require measuring current in a over-current detection as fast as 1μs.
high dv/dt common mode transients like motor control
and solenoid control, the INA253 is specifically design Table 1. Alternative Device Recommendations
to reject PWM signals with a settling time of <10µs.
Device Optimized Parameter Performance Trade-
As previously described, the typical current sensing INA210 Off
signal chain path includes the current sensing resistor, INA226 35μV VOS, Package: SC70-
the analog front-end, ADC and system controller. The INA301 6, QFN-10 No on-boad current
INA250 combines the shunt resistor and the current sensing resistor
sensing amplifier. The INA260 combines the current 10μV VOS, Package:
sensing resistor, measurement front-end and the ADC MSOP-10 No on-boad current
into one single device. sensing resistor
Signal Bandwidth, On-
Figure 3 shows the INA260 featuring the same Board Comparator No on-boad current
precision, integrated sensing resistor, pairing it with a sensing resistor
16-bit, precision ADC optimized for current sensing
applications. This combination provides an even higher Table 2. Related Documentation
performance measurement capability than the INA250
resulting in a maximum measurement gain error of SBOA197 Integrated-Resistor Current Sensors
0.5% over the entire temperature range and a Simplify PCB Design
maximum input offset current of 5mA. SBOA165
SBOA167 Precision Current Measurements on High-
SBOA169 Voltage Power Supply Rails

Integrating the Current Sensing Signal Path

Precision, Low-Side Current Measurement

2 Integrating the Current Sensing Resistor Scott Hill, Current Sensing Products SBOA170B – October 2016 – Revised July 2018

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1.1 Trademarks

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