Problem 8.17
a) If the power spectral density of the additive noise is Sn(f ), then the PSD of the noise at the
output of the prewhitening filter is
Sν(f ) = Sn(f )|Hp(f )|2
In order for Sν(f ) to be flat (white noise), Hp(f ) should be such that
1
Hp(f ) = Sn(f )
2) Let hp(t) be the impulse response of the prewhitening filter Hp(f ). That is, hp(t) = F −1[Hp(f )].
Then, the input to the matched filter is the signal s˜(t) = s(t) hp(t). The frequency response of
the filter matched to s˜(t) is
S˜m(f ) = S˜∗(f )e−j2πft0 == S∗(f )Hp∗(f )e−j2πft0
where t0 is some nominal time-delay at which we sample the filter output.
3) The frequency response of the overall system, prewhitening filter followed by the matched filter,
is S∗(f ) e−j2πft0
Sn(f )
G(f ) = S˜m(f )Hp(f ) = S∗(f )|Hp(f )|2e−j2πft0 =
4) The variance of the noise at the output of the generalized matched filter is
σ2 = ∞ ∞ |S(f )|2
df
Sn(f )|G(f )|2df =
−∞ Sn(f )
−∞
At the sampling instant t = t0 = T , the signal component at the output of the matched filter is
∞∞
Y (f )ej2πfT df =
y(T ) = s(τ )g(T − τ )dτ
=
−∞ −∞
∞ S∗(f ) ∞ |S(f )|2
−∞ S(f ) Sn(f ) df = −∞ Sn(f ) df
Hence, the output SNR is
y2(T ) ∞ |S(f )|2
SNR = = df
σ2 −∞ Sn(f )
Problem 8.18
The bandwidth of the bandpass channel is
W = 3300 − 300 = 3000 Hz
In order to transmit 9600 bps with a symbol rate R = 2400 symbols per second, the number of
information bits per symbol should be
k = 9600 = 4
2400
Hence, a 24 = 16 QAM signal constellation is needed. The carrier frequency fc is set to 1800 Hz,
which is the mid-frequency of the frequency band that the bandpass channel occupies. If a pulse
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with raised cosine spectrum and roll-off factor α is used for spectral shaping, then for the bandpass
signal with bandwidth W
R = 1200(1 + α) = 1500
and
α = 0.25
A sketch of the spectrum of the transmitted signal pulse is shown in the next figure.
1/2T
-3300 -1800 -300 300 600 1800 3300 f
3000
Problem 8.19
The channel bandwidth is W = 4000 Hz.
(a) Binary PSK with a pulse shape that has α= 1 . Hence
2
1
(1 + α) = 2000
2T
and 1 = 2667, the bit rate is 2667 bps.
T
1 1
(b) Four-phase PSK with a pulse shape that has α = 2 . From (a) the symbol rate is T = 2667 and
the bit rate is 5334 bps.
(c) M =8 QAM with a pulse shape that has α= 1 . From (a), the symbol rate is 1 = 2667 and
2 T
3
hence the bit rate T = 8001 bps.
(d) Binary FSK with noncoherent detection. Assuming that the frequency separation between the
two frequencies is ∆f = 1 , where 1 is the bit rate, the two frequencies are fc + 1 and fc − 1 .
T T 2T 2T
1 1
Since W = 4000 Hz, we may select 2T = 1000, or, equivalently, T = 2000. Hence, the bit rate is
2000 bps, and the two FSK signals are orthogonal.
(e) Four FSK with noncoherent detection. In this case we need four frequencies with separation
of 1 between adjacent frequencies. We select f1 = fc − 1.5 , f2 = fc − 1 , f3 = fc + 1 , and
T T 2T 2T
1.5 1 1
f4 = fc + T , where 2T = 500 Hz. Hence, the symbol rate is T = 1000 symbols per second and
since each symbol carries two bits of information, the bit rate is 2000 bps.
(f) M = 8 FSK with noncoherent detection. In this case we require eight frequencies with frequency
separation of 1 = 500 Hz for orthogonality. Since each symbol carries 3 bits of information, the
T
bit rate is 1500 bps.
Problem 8.20
1) The bandwidth of the bandpass channel is
W = 3000 − 600 = 2400 Hz
Since each symbol of the QPSK constellation conveys 2 bits of information, the symbol rate of
transmission is 2400
R = = 1200 symbols/sec
2
Thus, for spectral shaping we can use a signal pulse with a raised cosine spectrum and roll-off factor
α = 1, that is
Xrc(f ) = T [1 + cos(πT |f |)] = 1 cos2 π|f |
2 2400 2400
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